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NCP1653, NCP1653A Compact, Fixed-Frequency, Continuous Conduction Mode PFC Controller
The NCP1653 is a controller designed for Continuous Conduction Mode (CCM) Power Factor Correction (PFC) boost circuits. It operates in the follower boost or constant output voltage in 67 or 100 kHz fixed switching frequency. Follower boost offers the benefits of reduction of output voltage and hence reduction in the size and cost of the inductor and power switch. Housed in a DIP-8 or SO-8 package, the circuit minimizes the number of external components and drastically simplifies the CCM PFC implementation. It also integrates high safety protection features. The NCP1653 is a driver for robust and compact PFC stages.
Features http://onsemi.com MARKING DIAGRAMS
8 8 1 PDIP-8 P SUFFIX CASE 626 8 1 SO-8 D SUFFIX CASE 751 NCP1653 AWL YYWW 1 8 N1653 ALYW G 1 A suffix A WL, L YY, Y WW, W G 1 = 67 kHz option = Assembly Location = Wafer Lot = Year = Work Week = Pb-Free Package 1 8 1653A ALYW G 8 NCP1653A AWL YYWW
* * * * * * * * * * * * * * * * * *
IEC1000-3-2 Compliant Continuous Conduction Mode Average Current-Mode or Peak Current-Mode Operation Constant Output Voltage or Follower Boost Operation Very Few External Components Fixed Switching Frequency: 67 kHz = NCP1653A, Fixed Switching Frequency: 100 kHz = NCP1653 Soft-Start Capability VCC Undervoltage Lockout with Hysteresis (8.7 / 13.25 V) Overvoltage Protection (107% of Nominal Output Level) Undervoltage Protection or Shutdown (8% of Nominal Output Level) Programmable Overcurrent Protection Programmable Overpower Limitation Thermal Shutdown with Hysteresis (120 / 150_C) Pb-Free Packages are Available TV & Monitors PC Desktop SMPS AC Adapters SMPS White Goods
EMI Filter Output
PIN CONNECTIONS
FB 1 Vcontrol 2 In 3 CS 4 (Top View) 8 VCC 7 Drv 6 Gnd 5 VM
Typical Applications
ORDERING INFORMATION
AC Input
See detailed ordering and shipping information in the package dimensions section on page 18 of this data sheet.
15 V FB VCC Vcontrol Drv In Gnd CS VM NCP1653
Figure 1. Typical Application Circuit
(c) Semiconductor Components Industries, LLC, 2005
1
December, 2005 - Rev. 4
Publication Order Number: NCP1653/D
NCP1653, NCP1653A
Iin Vin L IL Output Voltage (Vout)
AC Input
EMI Filter
Cfilter RCS IL
Cbulk on off
RFB
IFB Vcontrol
1
FB / SD 9V
Current Mirror
Vreg
2
300 k 9V Ccontrol
96% I ref
I ref I FB
0
1
1
0
VCC
13.25 V / 8.7 V
Regulation Block UVLO
- +
VCC
8
18 V
Overvoltage Protection (IFB > 107% Iref) Shutdown / UVP (IFB < 8% Iref) 4% Iref Hysteresis VCC Reference Block
Vcontrol R1 R1 = constant Icontrol = Current Mirror Overpower Limitation (IS Ivac > 3 nA2) RMISIvac 2 Icontrol
&
Rvac
12 k
In
3
9V
Ivac Cvac
Turn on VM Internal Bias
5
IM 9V RM Vref Ich
-
VM = Thermal Shutdown (120 / 150 C) PFC Modulation
x
CM
Overcurrent Protection (IS > 200 mA)
CS Current Mirror VCC 9V Drv
4
IS RS
+ Cramp Gnd 0 1
+
Vramp 67 or 100 kHz clock
OR
R S
Q Output Driver
7
6
Figure 2. Functional Block Diagram
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NCP1653, NCP1653A
PIN FUNCTION DESCRIPTION
Pin 1 Symbol FB / SD Name Feedback / Shutdown Function This pin receives a feedback current IFB which is proportional to the PFC circuit output voltage. The current is for output regulation, output overvoltage protection (OVP), and output undervoltage protection (UVP). When IFB goes above 107% Iref, OVP is activated and the Drive Output is disabled. When IFB goes below 8% Iref, the device enters a low-consumption shutdown mode. The voltage of this pin Vcontrol directly controls the input impedance and hence the power factor of the circuit. This pin is connected to an external capacitor Ccontrol to limit the Vcontrol bandwidth typically below 20 Hz to achieve near unity power factor. The device provides no output when Vcontrol = 0 V. Hence, Ccontrol also works as a soft-start capacitor. This pin sinks an input-voltage current Ivac which is proportional to the RMS input voltage Vac. The current Ivac is for overpower limitation (OPL) and PFC duty cycle modulation. When the product (ISIvac) goes above 3 nA2, OPL is activated and the Drive Output duty ratio is reduced by pulling down Vcontrol indirectly to reduce the input power. This pin sources a current IS which is proportional to the inductor current IL. The sense current IS is for overcurrent protection (OCP), overpower limitation (OPL) and PFC duty cycle modulation. When IS goes above 200 mA, OCP is activated and the Drive Output is disabled. This pin provides a voltage VM for the PFC duty cycle modulation. The input impedance of the PFC circuit is proportional to the resistor RM externally connected to this pin. The device operates in average current-mode if an external capacitor CM is connected to the pin. Otherwise, it operates in peak current-mode. - This pin provides an output to an external MOSFET. This pin is the positive supply of the device. The operating range is between 8.75 V and 18 V with UVLO start threshold 13.25 V.
2
Vcontrol
Control Voltage / Soft-Start
3
In
Input Voltage Sense
4
CS
Input Current Sense Multiplier Voltage
5
VM
6 7 8
GND Drv VCC
The IC Ground Drive Output Supply Voltage
MAXIMUM RATINGS
Rating FB, Vcontrol, In, CS, VM Pins (Pins 1-5) Maximum Voltage Range Maximum Current Drive Output (Pin 7) Maximum Voltage Range Maximum Current Range (Note 2) Power Supply Voltage (Pin 8) Maximum Voltage Range Maximum Current Power Dissipation and Thermal Characteristics P suffix, Plastic Package, Case 626 Maximum Power Dissipation @ TA = 70C Thermal Resistance Junction-to-Air D suffix, Plastic Package, Case 751 Maximum Power Dissipation @ TA = 70C Thermal Resistance Junction-to-Air Operating Junction Temperature Range Storage Temperature Range Symbol Vmax Imax Vmax Imax Vmax Imax Value -0.3 to +9 100 -0.3 to +18 1.5 -0.3 to +18 100 Unit V mA V A V mA
PD RqJA PD RqJA TJ Tstg
800 100 450 178 -40 to +125 -65 to +150
mW C/W mW C/W C C
1. Maximum Ratings are those values beyond which damage to the device may occur. Exposure to these conditions or conditions beyond those indicated may adversely affect device reliability. Functional operation under absolute maximum-rated is not implied. Functional operation should be restricted to the Recommended Operating Conditions. A. This device series contains ESD protection and exceeds the following tests: Pins 1-8: Human Body Model 2000 V per MIL-STD-883, Method 3015. Machine Model Method 190 V. B. This device contains Latchup protection and exceeds 100 mA per JEDEC Standard JESD78. 2. Guaranteed by design.
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NCP1653, NCP1653A
ELECTRICAL CHARACTERISTICS (For typical values TJ = 25C. For min/max values, TJ = -40C to +125C, VCC = 15 V,
IFB = 100 mA, Ivac = 30 mA, IS = 0 mA, unless otherwise specified) Characteristics OSCILLATOR Switching Frequency Maximum Duty Cycle (VM = 0 V) (Note 3) GATE DRIVE Gate Drive Resistor Output High and Draw 100 mA out of Drv pin (Isource = 100 mA) Output Low and Insert 100 mA into Drv pin (Isink = 100 mA) Gate Drive Rise Time from 1.5 V to 13.5 V (Drv = 2.2 nF to Gnd) Gate Drive Fall Time from 13.5 V to 1.5 V (Drv = 2.2 nF to Gnd) 7 ROH ROL 7 7 tr tf Iref IregL/Iref Rcontrol Vcontrol(max) Icontrol(max) VFB1 5.0 2.0 - - 9.0 6.6 88 61.5 20 18 - - W W ns ns mA % kW V mA V V % mA ns % % mA ns NCP1653 NCP1653A 7 7 fSW Dmax 90 60.3 94 102 67 - 110 73.7 - kHz % Pin Symbol Min Typ Max Unit
FEEDBACK / OVERVOLTAGE PROTECTION / UNDERVOLTAGE PROTECTION Reference Current (VM = 3 V) Regulation Block Ratio Vcontrol Pin Internal Resistor Maximum Control Voltage (IFB = 100 mA) Maximum Control Current (Icontrol(max) = Iref / 2) Feedback Pin Voltage (IFB = 100 mA) Feedback Pin Voltage (IFB = 200 mA) Overvoltage Protection OVP Ratio Current Threshold Propagation Delay Undervoltage Protection (VM = 3 V) UVP Activate Threshold Ratio UVP Deactivate Threshold Ratio UVP Lockout Hysteresis Propagation Delay CURRENT SENSE Current Sense Pin Offset Voltage (IS = 100 mA) Overcurrent Protection Threshold (VM = 1 V) OVERPOWER LIMITATION Input Voltage Sense Pin Internal Resistor Over Power Limitation Threshold Sense Current Threshold (Ivac = 30 mA, VM = 3 V) Sense Current Threshold (Ivac = 100 mA, VM = 3 V) CURRENT MODULATION PWM Comparator Reference Voltage Multiplier Current (Vcontrol = Vcontrol(max), Ivac = 30 mA, IS = 25 mA) Multiplier Current (Vcontrol = Vcontrol(max), Ivac = 30 mA, IS = 75 mA) Multiplier Current (Vcontrol = Vcontrol(max) / 10, Ivac = 30 mA, IS = 25 mA) Multiplier Current (Vcontrol = Vcontrol(max) / 10, Ivac = 30 mA, IS = 75 mA) THERMAL SHUTDOWN Thermal Shutdown Threshold (Note 3) Thermal Shutdown Hysteresis 3. Guaranteed by design. - - TSD - 150 - - 30 - - C C 5 5 Vref IM1 IM2 IM3 IM4 2.25 1.0 3.2 10 30 2.62 2.85 9.5 35 103.5 2.75 5.8 18 58 180 V mA mA mA mA 4 3-4 4 Rvac(int) IS x Ivac IS(OPL1) IS(OPL2) - - 80 24 12 3.0 100 32 - - 140 48 kW nA2 mA mA 4 4 VS IS(OCP) 0 185 10 200 30 215 mV mA 1 1 2 2 2 1 1 IOVP/Iref IOVP tOVP 1 IUVP(on)/Iref IUVP(off)/Iref IUVP(H) tUVP 4.0 7.0 4.0 - 8.0 12 8.0 500 15 20 - - 104 - - 107 214 500 - 230 - 192 95 - - - 1.0 1.3 204 96 300 2.4 100 1.5 1.8 208 98 - - - 1.9 2.2
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NCP1653, NCP1653A
ELECTRICAL CHARACTERISTICS (For typical values TJ = 25C. For min/max values, TJ = -40C to +125C, VCC = 15 V,
IFB = 100 mA, Ivac = 30 mA, IS = 0 mA, unless otherwise specified) Characteristics SUPPLY SECTION Supply Voltage UVLO Startup Threshold Minimum Operating Voltage after Startup UVLO Hysteresis Supply Current: Startup (VCC = VCC(on) - 0.2 V) Startup (VCC < 4.0 V, IFB = 200 mA) Startup (4.0 V < VCC < VCC(on) - 0.2 V, IFB = 200 mA) Startup (VCC < VCC(on) - 0.2 V, IFB = 0 mA) (Note 4) Operating (VCC = 15 V, Drv = open, VM = 3 V) Operating (VCC = 15 V, Drv = 1 nF to Gnd, VM = 1 V) Shutdown (VCC = 15 V and IFB = 0 A) 8 VCC(on) VCC(off) VCC(H) 8 Istup Istup1 Istup2 Istup3 ICC1 ICC2 Istdn - - - - - - - 18 0.95 21 21 3.7 4.7 33 50 1.5 50 50 5.0 6.0 50 mA mA mA mA mA mA mA 12.25 8.0 4.0 13.25 8.7 4.55 14.5 9.5 - V V V Pin Symbol Min Typ Max Unit
4. Please refer to the "Biasing the Controller" Section in the Functional Description.
TYPICAL CHARACTERISTICS
110 fSW, SWITCHING FREQUENCY (kHz) 105 100 95 90 85 80 75 70 65 60 -50 -25 0 25 50 75 100 125 NCP1653A Dmax, MAXIMUM DUTY CYCLE (%) NCP1653 100 99 98 97 96 95 94 93 92 91 90 -50 -25 0 25 50 75 100 125 VM = 0 V
TJ, JUNCTION TEMPERATURE (C)
TJ, JUNCTION TEMPERATURE (C)
Figure 3. Switching Frequency vs. Temperature
Figure 4. Maximum Duty Cycle vs. Temperature
ROH & ROL, GATE DRIVE RESISTANCE (W)
14 Iref, REFERENCE CURRENT (mA) 75 100 125 12 10 8 6 4 2 0 -50 ROH
205 204 203 202 201 200 199 198 197 196 195 -50 -25 0 25 50 75 100 125
ROL
-25
0
25
50
TJ, JUNCTION TEMPERATURE (C)
TJ, JUNCTION TEMPERATURE (C)
Figure 5. Gate Drive Resistance vs. Temperature
Figure 6. Reference Current vs. Temperature
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NCP1653, NCP1653A
TYPICAL CHARACTERISTICS
3 Vcontrol, CONTROL VOLTAGE (V) 2.5 2 1.5 1 0.5 0 100 TJ = 125C TJ = -40C REGULATION BLOCK RATIO (%) TJ = 25C 100 99 98 97 96 95 94 93 92 91 90 -50 -25 0 25 50 75 100 125
120
140
160
180
200
220
IFB, FEEDBACK CURRENT (mA)
TJ, JUNCTION TEMPERATURE (C)
Figure 7. Regulation Block
Figure 8. Regulation Block Ratio vs. Temperature
2.5 FEEDBACK PIN VOLTAGE (V)
3.0 MAXIMUM CONTROL VOLTAGE (V) 2.9 2.8 2.7 2.6 2.5 2.4 2.3 2.2 2.1 2.0 -50 -25 0 25 50 75 100 125
2 IFB = 200 mA 1.5 IFB = 100 mA 1
0.5
0 -50
-25
0
25
50
75
100
125
TJ, JUNCTION TEMPERATURE (C)
TJ, JUNCTION TEMPERATURE (C)
Figure 9. Maximum Control Voltage vs. Temperature
OVERVOLTAGE PROTECTION RATIO (%) 2.5 FEEDBACK PIN VOLTAGE (V) 120 118 116 114 112 110 108 106 104 102 100 -50
Figure 10. Feedback Pin Voltage vs. Temperature
2
TJ = -40C
1.5 TJ = 25C TJ = 125C
1
0.5
0 0 50 100 150 200 250 IFB, FEEDBACK PIN CURRENT (mA)
-25
0
25
50
75
100
125
TJ, JUNCTION TEMPERATURE (C)
Figure 11. Feedback Pin Voltage vs. Feedback Current
Figure 12. Overvoltage Protection Ratio vs. Temperature
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NCP1653, NCP1653A
TYPICAL CHARACTERISTICS
OVERVOLTAGE PROTECTION THRESHOLD (mA) 230 UNDERVOLTAGE PROTECTION THRESHOLD RATIO (%) 225 220 215 210 205 200 -50 16 14 12 10 8 6 4 2 0 -50 -25 0 25 50 75 100 125 IUVP(on)/Iref IUVP(off)/Iref
-25
0
25
50
75
100
125
TJ, JUNCTION TEMPERATURE (C)
TJ, JUNCTION TEMPERATURE (C)
Figure 13. Overvoltage Protection Threshold vs. Temperature
100 OVERCURRENT PROTECTION THRESHOLD (mA) 90 80 70 60 50 40 30 20 10 0 0 50 100 150 200 250 IS, SENSE CURRENT (mA) TJ = -40 C TJ = 25 C 210 208 206 204 202 200 198 196 194 192 190 -50
Figure 14. Undervoltage Protection Thresholds vs. Temperature
CURRENT SENSE PIN VOLTAGE (mV)
TJ = 125 C
-25
0
25
50
75
100
125
TJ, JUNCTION TEMPERATURE (C)
Figure 15. Current Sense Pin Voltage vs. Sense Current
OVERPOWER LIMITATION THRESHOLD (nA2) 4 3.5 3 2.5 2 1.5 1 0.5 0 -50 0 25 50 75 100 125 Ivac = 100 mA Ivac = 30 mA 7 6 Vvac, IN PIN VOLTAGE (V) 5 4 3 2 1 0 -25
Figure 16. Overcurrent Protection Threshold vs. Temperature
TJ = -40 C TJ = 25 C TJ = 125 C
0
50
100
150
200
TJ, JUNCTION TEMPERATURE (C)
Ivac, INPUT-VOLTAGE CURRENT (mA)
Figure 17. Overpower Limitation Threshold vs. Temperature
Figure 18. In Pin Voltage vs. Input-Voltage Current
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NCP1653, NCP1653A
TYPICAL CHARACTERISTICS
PWM COMPARATOR REF. VOLTAGE (V) 3 MAXIMUM CONTROL CURRENT (mA) 2.9 2.8 2.7 2.6 2.5 2.4 2.3 2.2 2.1 2 -50 -25 0 25 50 75 100 125 200 180 160 140 120 100 80 60 40 20 Icontrol = 0 -50 -25 Ivac = 30 mA Vcontrol = Vcontrol(max) IS Ivac 2IM 0 25 50 75 100 125 derived from the (eq.8) IS = 75 mA IS = 25 mA
TJ, JUNCTION TEMPERATURE (C)
TJ, JUNCTION TEMPERATURE (C)
Figure 19. PWM Comparator Reference Voltage vs. Temperature
10% OF MAXIMUM CONTROL CURRENT (mA) 20 SUPPLY VOLTAGE UNDERVOLTAGE LOCKOUT THRESHOLDS (V) 18 16 14 12 10 8 6 4 2 Ivac = 30 mA Vcontrol = 10 % Vcontrol(max) Icontrol = -25 IS Ivac 2IM 0 25 50 75 100 125 derived from the (eq.8) IS = 75 mA IS = 25 mA 20 18 16 14 12 10 8 6 4 2 0 -50
Figure 20. Maximum Control Current vs. Temperature
VCC(on)
VCC(off)
0 -50
-25
0
25
50
75
100
125
TJ, JUNCTION TEMPERATURE (C)
TJ, JUNCTION TEMPERATURE (C)
Figure 21. 10% of Maximum Control Current vs. Temperature
80 70 60 50 40 30 20 10 0 -50 0 25 Istup Istdn 6 5 4 3 2 1
Figure 22. Supply Voltage Undervoltage Lockout Thresholds vs. Temperature
SUPPLY CURRENT IN STARTUP AND SHUTDOWN MODE (mA)
OPERATING SUPPLY CURRENT (mA)
ICC2, 1 nF Load
ICC1, No Load
VCC = 15 V 0 -50 -25 0 25 50 75 100 125
-25
50
75
100
125
TJ, JUNCTION TEMPERATURE (C)
TJ, JUNCTION TEMPERATURE (C)
Figure 23. Supply Current in Startup and Shutdown Mode vs. Temperature
Figure 24. Operating Supply Current vs. Temperature
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NCP1653, NCP1653A
FUNCTIONAL DESCRIPTION
Introduction
The NCP1653 is a Power Factor Correction (PFC) boost controller designed to operate in fixed-frequency Continuous Conduction Mode (CCM). It can operate in either peak current-mode or average current-mode. Fixed-frequency operation eases the compliance with EMI standards and the limitation of the possible radiated noise that may pollute surrounding systems. The CCM operation reduces the application di/dt and the resulting interference. The NCP1653 is designed in a compact 8-pin package which offers the minimum number of external components. It simplifies the design and reduces the cost. The output stage of the NCP1653 incorporates 1.5 A current capability for direct driving of the MOSFET in high-power applications. The NCP1653 is implemented in constant output voltage or follower boost modes. The follower boost mode permits one to significantly reduce the size of the PFC circuit inductor and power MOSFET. With this technique, the output voltage is not set at a constant level but depends on the RMS input voltage or load demand. It allows lower output voltage and hence the inductor and power MOSFET size or cost are reduced. Hence, NCP1653 is an ideal candidate in high-power applications where cost-effectiveness, reliability and high power factor are the key parameters. The NCP1653 incorporates all the necessary features to build a compact and rugged PFC stage. The NCP1653 provides the following protection features: 1. Overvoltage Protection (OVP) is activated and the Drive Output (Pin 7) goes low when the output voltage exceeds 107% of the nominal regulation level which is a user-defined value. The circuit automatically resumes operation when the output voltage becomes lower than the 107%. 2. Undervoltage Protection (UVP) is activated and the device is shut down when the output voltage goes below 8% of the nominal regulation level. The circuit automatically starts operation when the output voltage goes above 12% of the nominal regulation level. This feature also provides output open-loop protection, and an external shutdown feature. 3. Overpower Limitation (OPL) is activated and the Drive Output (Pin 7) duty ratio is reduced by pulling down an internal signal when a computed input power exceeds a permissible level. OPL is automatically deactivated when this computed input power becomes lower than the permissible level. 4. Overcurrent Protection (OCP) is activated and the Drive Output (Pin 7) goes low when the inductor current exceeds a user-defined value. The operation resumes when the inductor current becomes lower than this value.
5. Thermal Shutdown (TSD) is activated and the Drive Output (Pin 7) is disabled when the junction temperature exceeds 150_C. The operation resumes when the junction temperature falls down by typical 30_C.
CCM PFC Boost
A CCM PFC boost converter is shown in Figure 25. The input voltage is a rectified 50 or 60 Hz sinusoidal signal. The MOSFET is switching at a high frequency (typically 102 kHz in the NCP1653) so that the inductor current IL basically consists of high and low-frequency components. Filter capacitor Cfilter is an essential and very small value capacitor in order to eliminate the high-frequency component of the inductor current IL. This filter capacitor cannot be too bulky because it can pollute the power factor by distorting the rectified sinusoidal input voltage.
Iin Vin Cfilter IL L Vout Cbulk
Figure 25. CCM PFC Boost Converter PFC Methodology
The NCP1653 uses a proprietary PFC methodology particularly designed for CCM operation. The PFC methodology is described in this section.
IL Iin
t1 T
t2
time
Figure 26. Inductor Current in CCM
As shown in Figure 26, the inductor current IL in a switching period T includes a charging phase for duration t1 and a discharging phase for duration t2. The voltage conversion ratio is obtained in (eq.1).
t ) t2 Vout T +1 + t2 T * t1 Vin Vin + T * t1 Vout T
(eq.1)
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NCP1653, NCP1653A
The input filter capacitor Cfilter and the front-ended EMI filter absorbs the high-frequency component of inductor current IL. It makes the input current Iin a low-frequency signal only of the inductor current.
Iin + IL-50
(eq.2)
t1 CrampVref T * t1 VM + Vref * + Vref Cramp T T
(eq.6)
From (eq.3) and (eq.6), the input impedance Zin is re-formulated in (eq.7).
Zin + VM Vout Vref IL-50
(eq.7)
The suffix 50 means it is with a 50 or 60 Hz bandwidth of the original IL. From (eq.1) and (eq.2), the input impedance Zin is formulated.
T * t1 Vout V Zin + in + Iin T IL-50
(eq.3)
Because Vref and Vout are roughly constant versus time, the multiplier voltage VM is designed to be proportional to the IL-50 in order to have a constant Zin for PFC purpose. It is illustrated in Figure 28.
Power factor is corrected when the input impedance Zin in (eq.3) is constant or slowly varying in the 50 or 60 Hz bandwidth.
VM Ich + Cramp 0 1 Vref PFC Modulation - R + Vramp S Q
V in
I in IL
time
time VM time
clock Vref
Figure 28. Multiplier Voltage Timing Diagram
Vramp VM VM without filtering Clock Latch Set Latch Reset Output IM Inductor Current VM RM Ivac IS 2Icontrol
It can be seen in the timing diagram in Figure 27 that VM originally consists of a switching frequency ripple coming from the inductor current IL. The duty ratio can be inaccurately generated due to this ripple. This modulation is the so-called "peak current-mode". Hence, an external capacitor CM connected to the multiplier voltage VM pin (Pin 5) is essential to bypass the high-frequency component of VM. The modulation becomes the so-called "average current-mode" with a better accuracy for PFC.
5
VM =
Figure 27. PFC Duty Modulation and Timing Diagram
CM
RM
PFC Duty Modulation
The PFC duty modulation and timing diagram is shown in Figure 27. The MOSFET on time t1 is generated by the intersection of reference voltage Vref and ramp voltage Vramp. A relationship in (eq.4) is obtained.
It Vramp + VM ) ch 1 + Vref Cramp
(eq.4)
Figure 29. External Connection on the Multiplier Voltage Pin
The charging current Ich is specially designed as in (eq.5). The multiplier voltage VM is therefore expressed in terms of t1 in (eq.6).
Ich + Cramp Vref T
(eq.5)
The multiplier voltage VM is generated according to (eq.8).
RI I VM + M vac S 2 Icontrol
(eq.8)
Input-voltage current Ivac is proportional to the RMS input voltage Vac as described in (eq.9). The suffix ac
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NCP1653, NCP1653A
stands for the RMS. Ivac is a constant in the 50 or 60 Hz bandwidth. Multiplier resistor RM is the external resistor connected to the multiplier voltage VM pin (Pin 5). It is also constant. RM directly limits the maximum input power capability and hence its value affects the NCP1653 to operate in either "follower boost mode" or " constant output voltage mode".
2 Vac * 4 V V Ivac + [ ac (Rvac ) 12 kW) R vac
(eq.9)
Sense current IS is proportional to the inductor current IL as described in (eq.10). IL consists of the high-frequency component (which depends on di/dt or inductor L) and low-frequency component (which is IL-50).
R IS + CS IL RS
(eq.10)
over the bandwidth of 50 or 60 Hz and power factor is corrected. Practically, the differential-mode inductance in the front-ended EMI filter improves the filtering performance of capacitor Cfilter. Therefore, the multiplier capacitor CM is generally with a larger value comparing to the filter capacitor Cfilter. Input and output power (Pin and Pout) are derived in (eq.13) when the circuit efficiency is obtained or assumed. The variable Vac stands for the RMS input voltage.
V2 2 RS R vac Icontrol Vref Vac Pin + ac + Zin RM RCS Vout
(eq.13a)
I V T control ac Vout Pout + hPin + h 2 RS R vac Icontrol Vref Vac RM RCS Vout
(eq.13b)
Control current Icontrol is a roughly constant current that comes from the PFC output voltage Vout that is a slowly varying signal. The bandwidth of Icontrol can be additionally limited by inserting an external capacitor Ccontrol to the control voltage Vcontrol pin (Pin 2) in Figure 30. It is recommended to limit fcontrol, that is the bandwidth of Vcontrol (or Icontrol), below 20 Hz typically to achieve power factor correction purpose. Typical value of Ccontrol is between 0.1 mF and 0.33 mF.
Vreg 300 k I control = 96% I ref I ref IFB Regulation Block 2 Vcontrol Ccontrol Vcontrol R1
I V T control ac Vout
Follower Boost
The NCP1653 operates in follower boost mode when Icontrol is constant. If Icontrol is constant based on (eq.13), for a constant load or power demand the output voltage Vout of the converter is proportional to the RMS input voltage Vac. It means the output voltage Vout becomes lower when the RMS input voltage Vac becomes lower. On the other hand, the output voltage Vout becomes lower when the load or power demand becomes higher. It is illustrated in Figure 31.
V out (Traditional boost)
Figure 30. Vcontrol Low-Pass Filtering 1 Ccontrol u 2 p 300 kW fcontrol
V in (eq.11)
V out (Follower boost)
From (eq.7)-(eq.10), the input impedance Zin is re-formulated in (eq.12).
Zin + Zin + RM RCS Vac Vout IL 2 RS R vac Icontrol Vref IL-50
(eq.12) P out
time
RM RCS Vac Vout whenIL + IL-50 2 RS R vac Icontrol Vref
time
Figure 31. Follower Boost Characteristics Follower Boost Benefits
The multiplier capacitor CM is the one to filter the high-frequency component of the multiplier voltage VM. The high-frequency component is basically coming from the inductor current IL. On the other hand, the filter capacitor Cfilter similarly removes the high-frequency component of inductor current IL. If the capacitors CM and Cfilter match with each other in terms of filtering capability, IL becomes IL-50. Input impedance Zin is roughly constant
The follower boost circuit offers an opportunity to reduce the output voltage Vout whenever the RMS input voltage Vac is lower or the power demand Pout is higher. Because of the step-up characteristics of boost converter, the output voltage Vout will always be higher than the input voltage
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Vin even though Vout is reduced in follower boost operation. As a result, the on time t1 is reduced. Reduction of on time makes the loss of the inductor and power MOSFET smaller. Hence, it allows cheaper cost in the inductor and power MOSFET or allows the circuit components to operate at a lower stress condition in most of the time.
Output Feedback
power Pout. However, this output level is not constant and depending on different values of Vac and Pout. The follower boost operating area is illustrated in Figure 33.
Vout 96% Iref RFB Pout(min) 1 2 Pout(max)
The output voltage Vout of the PFC circuit is sensed as a feedback current IFB flowing into the FB pin (Pin 1) of the device. Since the FB pin voltage VFB1 is much smaller than Vout, it is usually neglected.
V * VFB1 V IFB + out [ out RFB RFB
(eq.14)
1. Pout increases, Vout decreases 2. Vac decreases, Vout decreases
V in Vac(min) Vac(max) Vac
Figure 33. Follower Boost Region Region (2): 96% x Iref < IFB < Iref
where RFB is the feedback resistor across the FB pin (Pin 1) and the output voltage referring to Figure 2. Then, the feedback current IFB represents the output voltage Vout and will be used in the output voltage regulation, undervoltage protection (UVP), and overvoltage protection (OVP).
Output Voltage Regulation
Feedback current IFB which represents the output voltage Vout is processed in a function with a reference current (Iref = 200 mA typical) as shown in regulation block function in Figure 32. The output of the voltage regulation block, low-pass filter on Vcontrol pin and the Icontrol = Vcontrol / R1 block is in Figure 30 is control current Icontrol. And the input is feedback current IFB. It means that Icontrol is the output of IFB and it can be described as in Figure 32. There are three linear regions including: (1) IFB < 96% x Iref, (2) 96% x Iref Iref. They are discussed separately as follows:
Icontrol Icontrol(max)
When IFB is between 96% and 100% of Iref (i.e., 96% RFB x Iref < Vout < RFB x Iref), the NCP1653 operates in constant output voltage mode which is similar to the follower boost mode characteristic but with narrow output voltage range. The regulation block output Vreg decreases linearly with IFB in the range from 96% of Iref to Iref. It gives a linear function of Icontrol in (eq.16).
Icontrol + Icontrol(max) Vout 1* 0.04 RFB Iref Vac
Pout RM RCS 0.04 2 RS R vac Vref Icontrol(max) h ac ) RFB Iref V
(eq.16)
Resolving (eq.16) and (eq.13),
Vout +
(eq.17)
96% Iref
Iref
IFB
Figure 32. Regulation Block Region (1): IFB < 96% x Iref
According to (eq.17), output voltage Vout becomes RFB x Iref when power is low (Pout 0). It is the maximum value of Vout in this operating region. Hence, it can be concluded that output voltage increases when power decreases. It is similar to the follower boost characteristic in (eq.15). On the other hand in (eq.17), output voltage Vout becomes RFB x Iref when RMS input voltage Vac is very high. It is the maximum value of Vout in this operating region. Hence, it can also be concluded that output voltage increases when RMS input voltage increases. It is similar to another follower boost characteristic in (eq.15). This characteristic is illustrated in Figure 34.
Vout Iref RFB 96% Iref RFB 1. Pout increases, Vout decreases 2. Vac decreases, Vout decreases V ac(min) Vac(max) Vac Pout(min) 1 2 Pout(max)
When IFB is less than 96% of Iref (i.e., Vout < 96% RFB x Iref), the NCP1653 operates in follower boost mode. The regulation block output Vreg is at its maximum value. Icontrol becomes its maximum value (i.e., Icontrol = Icontrol(max) = Iref/2 = 100 mA) which is a constant. (eq.13) becomes (eq.15).
Vout + h 2 RS R vac Icontrol(max) Vref Vac RM RCS Pout
(eq.15)
Figure 34. Constant Output Voltage Region Region (3): IFB > Iref
V T ac Pout
The output voltage Vout is regulated at a particular level with a particular value of RMS input voltage Vac and output
When IFB is greater than Iref (i.e., Vout > RFB x Iref), the NCP1653 provides no output or zero duty ratio. The regulation block output Vreg becomes 0 V. Icontrol also
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NCP1653, NCP1653A
becomes zero. The multiplier voltage VM in (eq.8) becomes its maximum value and generates zero on time t1. Then, Vout decreases and the minimum can be Vout = Vin in a boost converter. Going down to Vin, Vout automatically enters the previous two regions (i.e., follower boost region or constant output voltage region) and hence output voltage Vout cannot reach input voltage Vin as long as the NCP1653 provides a duty ratio for the operation of the boost converter. In conclusion, the NCP1653 circuit operates in one of the following conditions: Constant output voltage mode: The output voltage is regulated around the range between 96% and 100% of RFB x Iref. The output voltage is described in (eq.16). Its behavior is similar to a follower boost. Follower boost mode: The output voltage is regulated under 96% of RFB x Iref and Icontrol = Icontrol(max) = Iref/2 = 100 mA. The output voltage is described in (eq.15).
Overvoltage Protection (OVP)
IFB is always greater than 8% and 12% of the nominal level to enable the NCP1653 to operate. Hence, UVP happens when the output voltage is abnormally undervoltage, the FB pin (Pin 1) is opened, or the FB pin (Pin 1) is manually pulled low.
Soft-Start
The device provides no output (or no duty ratio) when the Vcontrol (Pin 2) voltage is zero (i.e., Vcontrol = 0 V). An external capacitor Ccontrol connected to the Vcontrol pin provides a gradually increment of the Vcontrol voltage (or the duty ratio) in the startup and hence provides a soft-start feature.
Current Sense
The device senses the inductor current IL by the current sense scheme in Figure 36. The device maintains the voltage at the CS pin (Pin 4) to be zero voltage (i.e., VS 0 V) so that (eq.10) can be formulated.
IL
When the feedback current IFB is higher than 107% of the reference current Iref (i.e., Vout > 107% RFB x Iref ), the Drive Output (Pin 7) of the device goes low for protection. The circuit automatically resumes operation when the feedback current becomes lower than 107% of the reference current Iref. The maximum OVP threshold is limited to 230 mA which corresponds to 230 mA x 1.92 MW + 2.5 V = 444.1 V when RFB = 1.92 MW (680 kW + 680 kW + 560 kW) and VFB1 = 2.5 V (for the worst case referring to Figure 11). Hence, it is generally recommended to use 450 V rating output capacitor to allow some design margin.
Undervoltage Protection (UVP)
ICC
RS
IS
CS + VS -
NCP1653 Gnd
RCS
IL
Figure 36. Current Sensing
This scheme has the advantage of the minimum number of components for current sensing and the inrush current limitation by the resistor RCS. Hence, the sense current IS represents the inductor current IL and will be used in the PFC duty modulation to generate the multiplier voltage VM, Overpower Limitation (OPL), and overcurrent protection.
Overcurrent Protection (OCP)
ICC2
Shutdown Istdn
Operating
Overcurrent protection is reached when IS is larger than IS(OCP) (200 mA typical). The offset voltage of the CS pin is typical 10 mV and it is neglected in the calculation. Hence, the maximum OCP inductor current threshold IL(OCP) is obtained in (eq.15).
I FB
8% I
ref
12% I ref
IL(OCP) +
RSIS(OCP) R +S RCS RCS
200 mA
(eq.18)
Figure 35. Undervoltage Protection
When the feedback current IFB is less than 8% of the reference current Iref (i.e., the output voltage Vout is less than 8% of its nominal value), the device is shut down and consumes less than 50 mA. The device automatically starts operation when the output voltage goes above 12% of the nominal regulation level. In normal situation of boost converter configuration, the output voltage Vout is always greater than the input voltage Vin and the feedback current
When overcurrent protection threshold is reached, the Drive Output (Pin 7) of the device goes low. The device automatically resumes operation when the inductor current goes below the threshold.
Input Voltage Sense
The device senses the RMS input voltage Vac by the sensing scheme in Figure 37. The internal current mirror is with a typical 4 V offset voltage at its input so that the current Ivac can be derived in (eq.9). An external capacitor
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NCP1653, NCP1653A
Cvac is to maintain the In pin (Pin 3) voltage in the calculation to always be the peak of the sinusoidal voltage due to very little current consumption (i.e., Vin = 2 Vac and Ivac 0). This Ivac current represents the RMS input voltage Vac and will be used in overpower limitation (OPL) and the PFC duty modulation.
V in Current Mirror
limited. The OPL is automatically deactivated when the product (IS x Ivac) becomes lower than the 3 nA2 level. This 3 nA2 level corresponds to the approximated input power (IL x Vac) to be smaller than the particular expression in (eq.20).
IS Ivac t 3 nA2 R IL @ CS RS 2 Vac @ t 3 nA2 Rvac ) 12 kW
(eq.20)
Rvac Ivac In 3
12 k 4V
RR ) 12 kW IL @ Vac t S vac 3 nA2 RCS 2 Biasing the Controller
Cvac
9V
Figure 37. Input Voltage Sensing
There is an internal 9 V ESD Zener Diode on the pin. Hence, the value of Rvac is recommended to be at least 938 k for possibly up to 400 V instantaneous input voltage.
Rvac 12 kW u 9 V*4 V 400 V * 9 V Rvac u 938 kW Overpower Limitation (OPL)
(eq.19)
It is recommended to add a typical 1 nF to 100 nF decoupling capacitor next to the VCC pin for proper operation. When the NCP1653 operates in follower boost mode, the PFC output voltage is not always regulated at a particular level under all application range of input voltage and load power. It is not recommended to make a low-voltage bias supply voltage by adding an auxiliary winding on the PFC boost inductor. Alternatively, it is recommended to get the VCC biasing supply from the second-stage power conversion stage as shown in Figure 39.
Vbulk AC EMI Input Filter
Sense current IS represents the inductor current IL and hence represents the input current approximately. Input-voltage current Ivac represents the RMS input voltage Vac and hence represents the input voltage. Their product (IS x Ivac) represents an approximated input power (IL x Vac).
V reg 300 k 2 96% I ref I ref I FB 0 1 Vcontrol
Vcc
Output Voltage
Second-stage Power Converter NCP1653
Figure 39. Recommended Biasing Scheme in Follower Boost Mode
Regulation Block Overpower Limitation
Figure 38. Overpower Limitation Reduces Vcontrol
When the product (IS x Ivac) is greater than a permissible level 3 nA2, the output Vreg of the regulation block is pulled to 0 V. It makes Vcontrol to be 0 V indirectly and VM is pulled to be its maximum. It generates the minimum duty ratio or no duty ratio eventually so that the input power is
When the NCP1653 operates in constant output voltage mode, it is possible to make a low-voltage bias supply by adding an auxiliary winding on the PFC boost inductor in Figure 40. In PFC boost circuit, the input is the rectified AC voltage and it is non-constant versus time that makes the auxiliary winding voltage also non-constant. Hence, the configuration in Figure 40 charges the voltages in capacitors C1 and C2 to nx(Vout - Vin) and nxVin and n is the turn ratio. As a result, the stack of the voltages is nxVout that is constant and can be used as a biasing voltage.
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NCP1653, NCP1653A
Vin Vout VCC Undervoltage Lockout (UVLO)
C2
C1
The device typically starts to operate when the supply voltage VCC exceeds 13.25 V. It turns off when the supply voltage VCC goes below 8.7 V. An 18 V internal ESD Zener Diode is connected to the VCC pin (Pin 8) to prevent excessive supply voltage. After startup, the operating range is between 8.7 V and 18 V.
Thermal Shutdown
VCC
Figure 40. Self-biasing Scheme in Constant Output Voltage Mode
An internal thermal circuitry disables the circuit gate drive and then keeps the power switch off when the junction temperature exceeds 150_C. The output stage is then enabled once the temperature drops below typically 120_C (i.e., 30_C hysteresis). The thermal shutdown is provided to prevent possible device failures that could result from an accidental overheating.
Output Drive
When the NCP1653 circuit is required to be startup independently from the second-stage converter, it is recommended to use a circuit in Figure 41. When there is no feedback current (IFB = 0 mA) applied to FB pin (Pin 1), the NCP1653 VCC startup current is as low (50 mA maximum). It is good for saving the current to charge the VCC capacitor. However, when there is some feedback current the startup current rises to as high as 1.5 mA in the VCC < 4 V region. That is why the circuit of Figure 41 can be implemented: a PNP bipolar transistor derives the feedback current to ground at low VCC levels (VCC < 4 V) so that the startup current keeps low and an initial voltage can be quickly built up in the VCC capacitor. The values in Figure 41 are just for reference.
Input Output
The output stage of the device is designed for direct drive of power MOSFET. It is capable of up to 1.5 A peak drive current and has a typical rise and fall time of 88 and 61.5 ns with a 2.2 nF load.
180k
180k
180k
1.5M 100uF 560k BC556 NCP1653
Figure 41. Recommended Startup Biasing Scheme
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NCP1653, NCP1653A
Application Schematic
680 k 680 k 560 k
Fuse
150 mH
KBU6K
600 mH
CSD04060
Input 90 Vac to 265 Vac
1 mF
100 nF 680 nF 4.7 M SPP20N60S
100 mF 450 V
Output 390 V
2 x 3.9 mH
33 nF
0.1
470 k 15 V NCP1653
2.85 k 4.5
330 nF
1 nF
1 nF
330 pF
56 k
10 k
Figure 42. 300 W 100 kHz Power Factor Correction Circuit Table 1. Total Harmonic Distortion and Efficiency
Input Voltage (V) 110 110 110 110 110 110 220 220 220 220 220 220 Input Power (W) 331.3 296.7 157.3 109.8 80.7 67.4 311.4 215.7 157.3 110.0 80.2 66.9 Output Voltage (V) 370.0 373.4 381.8 383.5 384.4 385.0 385.4 386.2 386.4 386.7 386.5 386.6 Output Current (A) 0.83 0.74 0.38 0.26 0.19 0.16 0.77 0.53 0.38 0.27 0.19 0.16 Power Factor 0.998 0.998 0.995 0.993 0.990 0.988 0.989 0.985 0.978 0.960 0.933 0.920 Total Harmonic Distortion (%) 4 4 7 9 10 10 9 8 9 11 14 15 Efficiency (%) 93 93 92 91 91 91 95 95 93 95 92 92
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NCP1653, NCP1653A
APPENDIX I - SUMMARY OF EQUATIONS IN NCP1653 BOOST PFC
Description Boost Converter Follower Boost Mode Constant Output Voltage Mode Same as Follower Boost Mode
t ) t2 Vout T +1 + t2 T * t1 Vin
Vout * Vin + t
Vout
Input Current Averaged by Filter Capacitor Nominal Output Voltage (IFB = 200 mA) Feedback Pin Voltage VFB1 Output Voltage Inductor Current Peak-Peak Ripple Control Current
t1 t +1 1 ) t2 T
Same as Follower Boost Mode Same as Follower Boost Mode
Iin + IL * 50 Vout(nom) + IFBRFB ) VFB1 [ IFBRFB + 200 mA @ RFB
Please refer to Figure 11.
Same as Follower Boost Mode
Vin t Vout t 192 mA @ RFB DIL(pk * pk) t 2 @ IL * 50 I Icontrol + Icontrol(max) + ref + 100 mA 2
192 mA @ RFB t Vout t 200 mA @ RFB
Same as Follower Boost Mode
Icontrol +
Icontrol(max) Vout 1* 0.04 RFBIref
and Icontrol t Icontrol(max) + 100 mA
Switching Frequency Minimum Inductor for CCM
f + 67 or 100 kHz V * Vin Vin 1 L u L(CRM) + out Vout DIL(pk * pk) f RR VV Zin + M CS ac out RSR vacIrefVref Pin + RS R vac Iref Vref Vac RM RCS Vout hRS R vac Iref Vref Vac RM RCS Vout
Same as Follower Boost Mode Same as Follower Boost Mode
Input Impedance
Zin + Pin +
RM RCS Vac Vout 2RS R vac Icontrol Vref 2RSR vacVref IcontrolVac RMRCS Vout h2 RS R vac Vref Icontrol Vac RM RCS Vout
Input Power
Output Power
Pout + hPin +
Pout +
Maximum Input Power when Icontrol = 100 mA Current Limit
RR IVV Pin(max) + Pin + S vac ref ref ac RM RCS Vout IL(OCP) + IL @ VAC t RS @ 200 mA RCS RS Rvac ) 12 kW @ 3 nA2 RCS 2
Circuit will enter follower boost region when maximum power is reached. Same as Follower Boost Mode
Power Limit
Same as Follower Boost Mode
Output Overvoltage
Vout(OVP) + 107% @ Vout(nom) [ 214 mA @ RFB Vout(UVP * on) + 8% @ Vout(nom) [ 16 mA @ RFB Vout(UVP * off) + 12% @ Vout(nom) [ 24 mA @ RFB R ) 12 kW Rvac u 938 kW and R vac + vac 2 Vref + 2.62 V
Same as Follower Boost Mode
Output Undervoltage
Same as Follower Boost Mode
Input Voltage Sense Pin Resistor Rvac PWM Comparator Reference Voltage
Same as Follower Boost Mode
Same as Follower Boost Mode
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NCP1653, NCP1653A
ORDERING INFORMATION
Device NCP1653P NCP1653PG NCP1653DR2 NCP1653DR2G NCP1653AP NCP1653APG NCP1653ADR2 NCP1653ADR2G Package PDIP-8 PDIP-8 (Pb-Free) SO-8 SO-8 (Pb-Free) PDIP-8 PDIP-8 (Pb-Free) SO-8 SO-8 (Pb-Free) Shipping 50 Units / Rail 50 Units / Rail 2500 Units / Tape & Reel 2500 Units / Tape & Reel 50 Units / Rail 50 Units / Rail 2500 Units / Tape & Reel 2500 Units / Tape & Reel 67 kHz Switching Frequency 100 kHz
For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specifications Brochure, BRD8011/D.
PACKAGE DIMENSIONS
PDIP-8 P SUFFIX CASE 626-05 ISSUE L
NOTES: 1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS). 3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. DIM A B C D F G H J K L M N MILLIMETERS MIN MAX 9.40 10.16 6.10 6.60 3.94 4.45 0.38 0.51 1.02 1.78 2.54 BSC 0.76 1.27 0.20 0.30 2.92 3.43 7.62 BSC --- 10_ 0.76 1.01 INCHES MIN MAX 0.370 0.400 0.240 0.260 0.155 0.175 0.015 0.020 0.040 0.070 0.100 BSC 0.030 0.050 0.008 0.012 0.115 0.135 0.300 BSC --- 10_ 0.030 0.040
8
5
-B-
1 4
F
NOTE 2
-A- L
C -T-
SEATING PLANE
J N D K
M
M TA
M
H
G 0.13 (0.005) B
M
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NCP1653, NCP1653A
PACKAGE DIMENSIONS
SO-8 D SUFFIX CASE 751-07 ISSUE AG
-X- A
8 5 NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. 6. 751-01 THRU 751-06 ARE OBSOLETE. NEW STANDARD IS 751-07. MILLIMETERS MIN MAX 4.80 5.00 3.80 4.00 1.35 1.75 0.33 0.51 1.27 BSC 0.10 0.25 0.19 0.25 0.40 1.27 0_ 8_ 0.25 0.50 5.80 6.20 INCHES MIN MAX 0.189 0.197 0.150 0.157 0.053 0.069 0.013 0.020 0.050 BSC 0.004 0.010 0.007 0.010 0.016 0.050 0_ 8_ 0.010 0.020 0.228 0.244
B
1 4
S
0.25 (0.010)
M
Y
M
-Y- G C -Z- H D 0.25 (0.010)
M SEATING PLANE
K
N
X 45 _
0.10 (0.004)
M
J
ZY
S
X
S
DIM A B C D G H J K M N S
SOLDERING FOOTPRINT*
1.52 0.060
7.0 0.275
4.0 0.155
0.6 0.024
1.270 0.050
SCALE 6:1 mm inches
*For additional information on our Pb-Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.
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NCP1653, NCP1653A
The product described herein (NCP1653) may be covered by one or more of the following U.S. patents: 6,362,067. There may be other patents pending.
ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. "Typical" parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT: N. American Technical Support: 800-282-9855 Toll Free Literature Distribution Center for ON Semiconductor USA/Canada P.O. Box 61312, Phoenix, Arizona 85082-1312 USA Phone: 480-829-7710 or 800-344-3860 Toll Free USA/Canada Japan: ON Semiconductor, Japan Customer Focus Center 2-9-1 Kamimeguro, Meguro-ku, Tokyo, Japan 153-0051 Fax: 480-829-7709 or 800-344-3867 Toll Free USA/Canada Phone: 81-3-5773-3850 Email: orderlit@onsemi.com ON Semiconductor Website: http://onsemi.com Order Literature: http://www.onsemi.com/litorder For additional information, please contact your local Sales Representative.
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NCP1653/D

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